• 专利附录
  • 专利说明
  • 权利要求
  • 类似技术
  • 同族专利
  • 引用文献
  • 法律状态
  • 优先权
    • 专利摘要:
    Converter and bidirectional conversion method from direct current to direct current without galvanic isolation. Converter and method of bidirectional conversion of direct current to direct current that achieves equivalent performance to a converter with double active bridge, while its topology does not require isolation transformer, so it is oriented to applications that do not require galvanic isolation, allowing its integration in a smaller size. The converter comprises a first bridge (B1), a second bridge (B2) and a transformer (T) with a primary winding (La) and a secondary winding (Lb). The primary winding (La) is connected to a first output port (Po1) of the first bridge (B1); and to a third input port (Pi3) of the second bridge (B2) through a first capacitor (C1); and the secondary winding (Lb) is connected to a second output port (Po2) of the first bridge (B1); and to a fourth input port (Pi4) of the second bridge (B2) through a second capacitor (C2). (Machine-translation by Google Translate, not legally binding)
    公开号:ES2706391A1
    申请号:ES201730842
    申请日:2017-06-27
    公开日:2019-03-28
    发明作者:Bautista Andres Barrado；Aleksandar Prodic
    申请人:Universidad Carlos III de Madrid；
    IPC主号:
    专利说明:

    [0001]
    [0002] Converter and bidirectional conversion method from direct current to direct current without galvanic isolation
    [0003]
    [0004] Object of the invention
    [0005]
    [0006] The present invention relates to the field of electric power management, and more specifically to a bidirectional direct current to direct current converter for applications that do not require galvanic isolation.
    [0007]
    [0008] BACKGROUND OF THE INVENTION
    [0009]
    [0010] DC-DC converters of the active double bridge (DAB) type are widely used in bidirectional energy management systems, such as energy storage or electric vehicles of all types (cars, planes, trains, etc). For example, US 5,027,264 A presents a basic scheme of a DAB converter in which a transformer is used to connect two bridges, each bridge consisting of four synchronized switches. From this basic scheme, various modifications have been developed, such as, for example, the one presented by US 5,500,791 A, which incorporates a plurality of output transformers in parallel to the main transformer, thus making it possible to distribute the input power among various loads. For its part, US 20110249472 A1 presents a DAB converter controlled by pulse width modulation (PWM, from the English 'Pulse Width Modulation).
    [0011]
    [0012] However, all implementations of the DAB topology known in the state of the art require galvanic isolation in the transformer (or transformers). In some cases additional coils are also required for proper operation; while in others the dispersion inductance of the transformer is used as a coupling coil, thus avoiding the use of additional coils. The weight and volume of these elements suppose serious limitations at the time of integrating the DAB converters, which imposes technological challenges at the time of incorporating them to vehicles, and makes it impossible to use them directly in smaller power supplies, such as those that are used for the feeding of microprocessors, set of programmable gates (FPGA, of the English 'Field Programmable Gate Array'), digital processor of signals (DSP, from English 'digital signal processor'), work stations, personal computers, etc.
    [0013]
    [0014] On the other hand, dual Active Half-Bridge (DAHB) topologies have been developed that avoid the use of transformers when connecting the two bridges by means of two pairs of coils and capacitors in series. However, the two necessary coils can still be problematic when integrating the device, and also the control options in the DAHB case are more limited than in the DAB case. For example, the DAHB topology does not allow control by simultaneous change of phase and both work cycles, which would not achieve advantages such as zero voltage switching (ZVS, Zero Voltage Switching) or zero current (ZCS, of English 'Zero Current Switching'), with constant frequency and for the whole range of powers, with different input and output voltages.
    [0015]
    [0016] Therefore, there is still a need in the state of the art for bidirectional converters that offer the advantages and freedom of operation of DAB converters, but with a lower volume and weight, and that allow their integration in a greater variety of systems than do not require galvanic isolation.
    [0017]
    [0018] Description of the invention
    [0019]
    [0020] The present invention solves the problems described above by means of a bidirectional CC-CC conversion scheme that uses a transformer as an equalizer between the two bridges, taking advantage of the dispersion inductances of said transformer, said dispersion inductances being supplemented in some implementations of the invention by means of external inductances. All the control options of the DAB scheme are thus maintained, without the need to resort to galvanic isolations.
    [0021]
    [0022] In a first aspect of the invention there is presented a DC-DC converter comprising at least a first bridge, a second bridge and a transformer, being able to comprise a greater number of bridges depending on the particular embodiment of the invention. Each bridge comprises at least four switches connected together, giving rise to two input ports and two output ports. Note that since it is a device that can operate bi-directionally, the terminology "ports of entry" and "ports of exit" is used exclusively to facilitate the understanding of the invention and does not imply any limitation as to the direction of the flow of current. In particular, note that they can be used as a load, for example a resistor, another source, a battery or a set of supercapacitors.
    [0023]
    [0024] In both bridges, the entry ports are those closest to the input source, following the direction of the current that flows from said input to the output load. In this way, the input ports of the first bridge are connected to said input source, and the output ports of the second bridge are connected to the output load, and the converter can also comprise additional capacitances in parallel with both the source and the load.
    [0025]
    [0026] The transformer, on the other hand, comprises a primary winding and a secondary winding, preferably with the same number of turns. That is, the windings of the transformer have a 1: 1 ratio, unlike in the DAB topology, whose relation is 1: n. The connection of said windings also changes with respect to the DAB topology, significantly modifying the functionality of said transformer. According to the converter of the present invention, each winding of the transformer connects an output port of the first bridge with an input port of the second bridge. In the case of the second bridge, the connection to the winding of the transformer is made through a blocking capacitor. Said blocking capacitor is therefore connected in series with a transformer inductance inductance. Additionally, particular implementations of the converter may comprise one or more additional auxiliary inductances in series with the parasitic inductance and the blocking capacitor.
    [0027]
    [0028] Preferably, the converter further comprises signal generating means that produce the control signals of the at least eight switches that make up the two bridges. The combination of said control signals gives rise to a periodic oscillatory intensity flow through the transformer (both in the primary winding and in the secondary winding, although with opposite signs). Preferably, said signal generating means can operate by phase shift modulation, by pulse width modulation, or by a combination of both. Also preferably, each period of the oscillatory intensity flow is formed by between four and eight segments, each with a different slope, which in some cases form an approximation to a sinusoidal signal.
    [0029]
    [0030] Preferably, the switches of both the first bridge and the second bridge are chosen from metal-oxide-semiconductor field effect transistors (MOSFET) and bipolar gate transistors ("Metal-oxide-semiconductor Field-effect Transistor") isolated (IGBT of the English 'Isolated Gate Bipolar Transistor'), although particular implementations of the invention can be made with any other type of switch known generally in the state of the art.
    [0031]
    [0032] In a second aspect of the invention a bidirectional CC-CC conversion method is presented comprising the following steps:
    [0033] i. Produce at least eight control signals that manage the operation of at least four switches of a first bridge and four switches of a second bridge. Said at least eight control signals are preferably rectangular signals, generated by pulse width modulation, phase shift modulation, or a combination of both.
    [0034] ii. Generate, thanks to the connections of the managed switches, a periodic oscillatory current flow in a transformer connected to said first bridge and second bridge. The transformer comprises a primary winding and a secondary winding, each of said windings being connected to an output port of the first bridge, and to an input port of the second bridge through a blocking capacitor, and sometimes through an additional inductance.
    [0035]
    [0036] Preferably, in the case of using phase shift modulation, the method comprises the step of producing the at least eight control signals, it comprises in turn inducing relative phase shifts between four pairs of control signals, each of said couples inverted among themselves (or what is the same, 180 ° out of phase with each other). Each pair of inverted control signals correspond to two switches connected to one of the ports that are connected to the transformer, that is, the output ports of the first bridge and the input ports of the second bridge.
    [0037]
    [0038] Note that any preferred option or particular implementation of the converter of the invention can also be applied to the method of the invention. Also, the elements of said converter can be adapted or configured to implement any step of the method of the invention, according to any particular implementation of both.
    [0039]
    [0040] Note also that the converter and conversion method of the invention can be used in traditional applications of the DAB architecture that do not require galvanic isolation, but can also be used advantageously to other sectors traditionally excluded from the applications of said architecture, such as the feeding of portable systems such as PDAs, mobiles, tablets, etc.
    [0041]
    [0042] In short, the converter and method of conversion described provide advantages over alternatives known in the state of the art. Compared with DAB architectures, they avoid the need for a transformer that provides galvanic isolation, reducing the volume and weight of the device and facilitating its integration. Compared with DAHB architectures, it is possible to integrate the necessary inductances between the first and second bridge in a single device (the transformer), also allowing greater control flexibility, and being able to operate, for example, in ZVS or ZCS mode. These and other advantages of the invention will be apparent in light of the detailed description thereof.
    [0043]
    [0044] Description of the figures
    [0045]
    [0046] In order to help a better understanding of the characteristics of the invention according to a preferred example of practical realization thereof, and to complement this description, the following figures are included as an integral part thereof, whose character is illustrative and non-limiting:
    [0047]
    [0048] Figure 1 presents a scheme of active double bridge converter (DAHB) known in the state of the art.
    [0049]
    [0050] Figure 2 exemplifies an active double bridge converter (DAB) scheme known in the state of the art.
    [0051]
    [0052] Figure 3 presents a bidirectional CC-CC converter scheme, according to a particular embodiment of the invention.
    [0053]
    [0054] Figure 4 illustrates possible offsets between the control signals of the switches, according to a particular embodiment of the invention.
    [0055]
    [0056] Figure 5 shows the resulting voltages at the exit of the first bridge and at the entrance of the second bridge associated with the control signals of figure 4.
    [0057]
    [0058] Figure 6 shows the current at the output of the primary winding of the transformer, according to the control signals of figure 4.
    [0059] PREFERRED EMBODIMENT OF THE INVENTION
    [0060]
    [0061] In this text, the term "comprises" and its derivations (such as "understanding", etc.) should not be understood in an excluding sense, that is, these terms should not be interpreted as excluding the possibility that what is described and defined can include more elements, stages, etc.
    [0062]
    [0063] Figure 1 shows a converter known in the state of the art, in particular of the DAHB type. The converter comprises a first bridge (B1) with four switches (S1, S2, S3, S4) connected to each other around a first input port (Pi1), a second input port (Pi2), a first output port (Po1) and a second output port (Po2). In the same way, the converter comprises a second bridge (B2) with four switches (S5, S6, S7, S8) connected to each other around a third input port (Pi3), a fourth input port (Pi4), a third exit port (Po3) and a fourth exit port (Po4). The first input port (Pi1) and the second input port (Pi2) of the first bridge (B1) are connected to an input source (Vin), and there may also be an input capacitor (Cin) in parallel. The third output port (Po3) and the fourth output port (Po4) of the second bridge (B2) are connected to the output load (Ro), and there may also be an output capacitor (Co) in parallel. In all cases, we will define VB1 as the voltage between the first output port (Po1) and the second output port (Po2) of the first bridge (B1); and we will define VB2 as the voltage between the third input port (Pi3) and the fourth input port (Pi4) of the second bridge (B2).
    [0064]
    [0065] Note that the nomenclature of input and output ports is used for explanatory purposes to facilitate the understanding of the invention and of the converters known in the state of the art. However, in the case of bidirectional devices, in the case of replacing the output load with another source, the input ports can act as output ports, and vice versa.
    [0066]
    [0067] In the particular case of the DAHB topology of Figure 1, the first output port (Po1) of the first bridge (B1) and the third input port (Pi3) of the second bridge (B2) are connected through a first inductance (L1) and a first capacitor (C1) in series. Likewise, the second output port (Po2) and the fourth input port (Pi4) are connected through a second inductance (L2) and a second capacitor (C2) in series.
    [0068] Figure 2 shows a DAB topology also known in the state of the art, which preserves the described configuration for the first bridge (B1), the second bridge (B2), the input source (Vin) and the output load ( Ro) of the DAHB case, modifying only the connection between bridges. In particular, the first bridge (B1) and the second bridge (B2) are connected through a transformer (T) with galvanic isolation. The transformer (T) comprises a primary winding (La) with a first number (N1) of turns, and a secondary winding (Lb) with a second number (N2) of turns. That is, a 1: n relation is established between the primary winding (La) and the secondary winding (Lb), with n equal to or different from 1.
    [0069]
    [0070] The primary winding (La) is connected at both ends to the first output port (Po1) and the second output port (Po2) of the first bridge (B1), also requiring a coil (L) in series at one of said ends . Similarly, the secondary winding (Lb) is connected at both ends to the third input port (Pi3) and the fourth input port (Pi4) of the second bridge (B2).
    [0071]
    [0072] Figure 3 finally presents a CC-CC converter according to a preferred embodiment of the invention, which in turn implements a preferred embodiment of the method of the invention. The CC-CC converter of the invention preserves the arrangement of the first bridge (B1), the second bridge (B2), the input source (Vin) and the output load (Ro) of the DAB and DAHB cases described. Also, it presents a transformer (T) between the first bridge (B1) and the second bridge (B2) as in the case of DAB. However, the disposition and characteristics of said transformer (T) show notable differences with the DAB case that modify its operation and the provided services.
    [0073]
    [0074] First, the arrangement of elements used prevents the transformer (T) of the invention from providing galvanic isolation to the converter, facilitating the integration of the overall device. Second, the ratio between the primary winding (La) and the secondary winding (Lb) is a 1: 1 ratio. That is, the primary winding (La) and the secondary winding (Lb) have the same number of turns (N). Third, unlike in the DAB topology, the primary winding (La) of the transformer (T) connects the first output port (Po1) of the first bridge (B1) and the third input port (Pi3) of the second bridge (B2). In the same way, the secondary winding (Lb) connects the second output port (Po2) and the fourth input port (Pi4). Both in the case of the third input port (Pi3) and the fourth input port (Pi4), the connection is made through blocking capacitors: a first capacitor (C1) and a second capacitor (C2).
    [0075] The figure also shows the parasitic inductances of the transformer (T): a magnetization inductance (Lm) in parallel with the primary winding (La), a first dispersion inductance (Ld1) in series with said primary winding (La) , and a second dispersion inductance (Ld2) in series with the secondary winding (Lb). Note that the topology of the present invention advantageously takes advantage of said parasitic inductances in the current conversion, which positively affects the integration of the device. However, particular embodiments of the present invention may comprise auxiliary inductances connected in series to the transformer inductance inductances.
    [0076]
    [0077] Figure 4 presents a preferred embodiment of the eight control signals (V gs 1, V gs 2, V gs 3, V gs 4, V gs 5, V gs 6, V gs 7, V gs 8) generated by the means of signal generation to control the eight switches (S1, S2, S3, S4, S5, S6, S7, S8) of the converter. These are periodic control signals of equal amplitude and mostly rectangular (taking into account deviations from the ideal rectangular shape of the implementation technology). The control signals are grouped into four pairs, with each pair of signals inverted, or 180 ° out of phase. Additionally, the pairs are out of phase with each other, with three different phase shifts (^, ^ 2, 93) comprised between 0 and 180 °, which may change depending on the particular implementation. The pairs of inverted control signals correspond to the following pairs of switches:
    [0078] - First switch (S1) and second switch (S2) of the first bridge (B1), joined by the first output port (Po1).
    [0079] - Third switch (S3) and fourth switch (S4) of the first bridge (B1), joined by the second output port (Po2).
    [0080] - Fifth switch (S5) and sixth switch (S6) of the second bridge (B2), joined by the third input port (Pi3).
    [0081] - Seventh switch (S7) and eighth switch (S8) of the second bridge (B2), joined by the fourth input port (Pi4).
    [0082]
    [0083] Figure 5 shows the voltages VB1 and VB2 resulting from applying the control signals (V gsi , V gs 2, V gs 3, V gs 4, V gs 5, V gs 6, V gs 7, V gs 8) of the figure 4 to the topology of figure 3. It is observed that both voltages VB1 and VB2 present periodic variations, with different amplitude and out of phase with each other.
    [0084]
    [0085] Finally, figure 6 presents the current (iLd1) generated at the output of the primary winding (La) of the transformer (T), as a consequence of the differences between VB1 and VB2 at each instant. It is observed that the phase distribution of the control signals (V gsi , V gs 2, V gs 3, V gs 4, V gs 5, V gs 6, V gs 7, V gs 8) generates a periodic current, being each period formed by six segments of different slope. Note that the current generated in the secondary winding (Lb) would have the same shape, but in the opposite direction. Note also that particular embodiments of the invention can employ other alternative control signals, using phase shift and / or pulse width modulation equivalent to those known in the state of the art for the DAB topology. In the same way, particular implementations of the invention can employ other topologies with a greater number of switches, also as known in the state of the art for DAB topologies.
    [0086]
    [0087] Note that the main objective of the DAHB is to eliminate the DAB transformer, for which two capacitors are introduced and the references of both bridges are joined, losing the galvanic isolation. In the DAHB the capacitors are therefore mandatory. The main advantage is that, by eliminating the transformer, the circuit can be integrated more and therefore it can be made smaller. In return, control possibilities are lost, both with respect to the DAB and the converter of the invention, the current is greatly increased by the mass (reference), and the galvanic isolation is lost as indicated above. Also, the DAHB mandatorily requires two inductances, one per branch. However, the DAB can operate with only one inductance, in some cases it being possible to use only the transformer dispersion inductance, and in other cases to add an external inductance to the transformer; as it occurs in the converter of the invention. In the DAB, the current by reference (mass) between the input and output bridge is zero, having galvanic isolation.
    [0088]
    [0089] For its part, the converter of the invention aims to maintain the properties of the DAB without the need for the isolation transformer, however an equalization transformer is necessary. In theory, the converter of the invention could operate without the first capacitor (C1) and the second capacitor (C2). However, the tolerances of the components and the control means that the signals are not absolutely symmetrical, making necessary in practice the first capacitor (C1) and the second capacitor (C2). The value of the first capacitor (C1) and the second capacitor (C2) can be chosen within the typical ranges used in DAHB schemes, although there is greater design flexibility. Likewise, in the converter of the invention all the control techniques used in the DAB can be applied, including control by triple phase displaced, being therefore more flexible than the DAHB, in which this control can not be implemented. This flexibility allows obtaining better yields, since ZVS or ZCS can be obtained in the transistors of the bridges, which allows a reduction of the losses by commutation, while reducing the effective current by them, which entails a reduction of the losses by conduction. Additionally, in the converter of the invention, the reference current (masses) between the first bridge (B1) and the second bridge (B2) is almost zero, as would happen with the DAB, but without the need for an isolation transformer. Finally, to optimize the DAHB it is necessary to work at a variable frequency, however the converter of the invention allows its optimization by operating at a constant frequency.
    [0090]
    [0091] In view of this description and figures, the person skilled in the art will be able to understand that the invention has been described according to some preferred embodiments thereof, but that multiple variations can be introduced in said preferred embodiments, without departing from the object of the invention such and how it has been claimed.
    权利要求:
    Claims (14)
    [1]
    1. Bidirectional DC to DC current converter without galvanic isolation comprising:
    - at least one first bridge (B 1 ) with at least four first switches (S 1 , S 2 , S 3 , S 4 ), and with a first input port (P i1 ) and a second input port (P i2) ) connected to an input source (V in );
    - at least one second bridge (B 2 ) with at least four seconds switches
    (S 5 , S 6 , S 7 , S 8 ), and with a third output port (P i3 ) and a fourth output port (P i4 ) connected to an output load (R 0 ); Y
    - a transformer (T) with a primary winding (L a ) and a secondary winding
    (L b );
    characterized in that:
    - the primary winding (L a) of the transformer (T) is connected to a first output port (P o1) of at least one first bridge (B 1) and a third input port (P i3) of at least one second bridge (B 2 ) through a first capacitor (C 1 ); Y
    - the secondary winding (L b ) of the transformer (T) is connected to a second output port (P o2 ) of the at least one first bridge (B 1 ); and a fourth input port (P i4 ) of the at least one second bridge (B 2 ) through a second capacitor (C 2 ).
    [2]
    2. Converter according to claim 1, characterized in that the primary winding (L a ) and the secondary winding (L b ) have the same number (N) of turns.
    [3]
    3. Converter according to any of the preceding claims, characterized in that it comprises at least one auxiliary inductance in series with a dispersion inductance (L d1 , L d2 ) of the transformer (T).
    [4]
    A converter according to any of the preceding claims, characterized in that it also comprises means for generating signals adapted to produce at least eight control signals (V gsi , V gs 2, V gs 3, V gs 4, V gs 5, V gs 6, V GS7 , V GS8 ) of the at least four first switches (S 1 , S 2 , S 3 , S 4 ) and the at least four second switches (S 5 , S 6 , S 7 , S 8 ) , with at least eight control signals (V gsi , V gs 2, V gs 3, V gs 4, V gs 5, V gs 6, V gs 7, V gs 8) configured to generate a periodic oscillatory current flow through the transformer (T).
    [5]
    5. Converter according to claim 4, characterized in that the signal generating means comprise phase shift modulation means.
    [6]
    Converter according to any of claims 4 and 5, characterized in that the signal generation means comprise pulse width modulation means.
    [7]
    7. Converter according to any of claims 4 to 6 characterized in that each period of the oscillatory current flow is formed by between four and eight segments of different slope.
    [8]
    8. Converter according to any of the preceding claims characterized in that the transformer (T) is an equalization transformer that does not provide galvanic isolation to the converter.
    [9]
    9. Converter according to any of the preceding claims characterized in that the at least four first switches (S1, S2, S3, S4) and the at least four second switches (S5, S6, S7, S8) are chosen from among transistors of metal-oxide-semiconductor field effect and isolated gate bipolar transistors.
    [10]
    10. Method of converting direct current to direct current comprising:
    - producing at least eight control signals (V gs 1, V gs 2, V gs 3, V gs 4, V gs 5, V gs 6, V gs 7, VGS8) from at least four first switches (S1, S2, S3, S4) of a first bridge (B1) and at least four second switches (S5, S6, S7, S8) of a second bridge (B2);
    characterized in that it further comprises:
    - generating a periodic oscillatory current flow through a transformer (T) comprising a primary winding (La) and a secondary winding (Lb); the primary winding (La) being connected to a first output port (Po1) of the first bridge (B1) and to a third input port (Pi3) of the second bridge (B2) through a first capacitor (C1); and the secondary winding (Lb) being connected to a second output port (Po2) of the first bridge (B1) and a fourth input port (Pi4) of the second bridge (B2) through a second capacitor (C2).
    [11]
    11. Conversion method according to claim 10 characterized in that the step of producing the at least eight control signals (VGS1, VGS2, VGS3, VGS4, VGS5, VGS6, VGS7, VGS8) comprises producing at least eight rectangular signals.
    [12]
    12. Conversion method according to any of claims 10 to 11, characterized in that the step of producing the at least eight control signals (V gs 1, V gs 2, V gs 3, V gs 4, V gs 5, V gs 6, V gs 7, V gs 8) comprises modular in phase shift.
    [13]
    13. Conversion method according to any of claims 10 and 12 characterized in that the step of producing the at least eight control signals (V gs 1, V gs 2, V gs 3, V gs 4, V gs 5, V gs 6, V gs 7, V gs 8) comprises modular in pulse width.
    [14]
    14. Conversion method according to claim 13 characterized in that the step of producing the at least eight control signals (VGS1, VGS2, VGS3, VGS4, VGS5, V gs 6, V gs 7, V gs 8) comprises:
    - inducing a first phase shift (^ 1) between a first pair of inverted control signals of the first bridge (VGS1, VGS2) and a second pair of inverted control signals of the first bridge (VGS3, VGS4);
    - inducing a second phase shift (^ 2) between the first pair of inverted control signals of the first bridge (VGS1, VGS2) and a third pair of inverted control signals of the second bridge (VGS5, VGS6); Y
    - inducing a third phase shift (^ 3) between the first pair of inverted control signals of the first bridge (VGS1, VGS2) and a fourth pair of inverted control signals of the second bridge (VGS7, VGS8).
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    同族专利:
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    引用文献:
    公开号 | 申请日 | 公开日 | 申请人 | 专利标题
    US20170085183A1|2015-09-22|2017-03-23|Infineon Technologies Austria Ag|System and Method for a Switched-Mode Power Supply Having a Transformer with a Plurality of Primary Windings|
    法律状态:
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